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Performance Analysis of Hybrid Cellular and Cell-free MIMO Network

Zhuoyin Dai*, Jingran Xu*, Xiaoli Xu*, Ruoguang Li* and Yong Zeng*\dagger
*National Mobile Communications Research Laboratory, Southeast University, Nanjing 210096, China
†Purple Mountain Laboratories, Nanjing 211111, China
Email: {zhuoyin_dai, jingran_xu, xiaolixu, ruoguangli, yong_zeng}@seu.edu.cn
Abstract

Cell-free wireless communication is envisioned as one of the most promising network architectures, which can achieve stable and uniform communication performance while improving the system energy and spectrum efficiency. The deployment of cell-free networks is envisioned to be a long-term evolutionary process, in which cell-free access points (APs) will be gradually introduced into the communication network and collaborate with the existing cellular base stations (BSs). To further explore the performance limits of hybrid cellular and cell-free networks, this paper develops a hybrid network model based on stochastic geometric toolkits, which reveals the coupling of the signal and interference from both the cellular and cell-free networks. Specifically, the conjugate beamforming is applied in hybrid cellular and cell-free networks, which enables user equipment (UE) to benefit from both cellular BSs and cell-free APs. The aggregate signal received from the hybrid network is approximated via moment matching, and coverage probability is characterized by deriving the Laplace transform of the interference. The analysis of signal strength and coverage probability is verified by extensive simulations.

I Introduction

The future wireless communication networks will witness a proliferation of mobile applications and unprecedented growth in wireless data. The realization of higher spectrum and energy efficiency with superior costs remains a challenging issue in current research. As one of the most prominent wireless technologies proposed in recent years, cell-free network is considered as a promising network architecture in the beyond fifth-generation (B5G) and sixth generation (6G) mobile communication system [1]. Different from traditional cellular systems, cell-free network is a user-centric coverage architecture that discards the traditional concept of cellular boundaries [2]. The central processing unit (CPU) controls the access points (APs) to cooperate to provide services to user equipment (UE) on the same time-frequency resources, thus realizing higher spatial multiplexing [3, 4]. Cell-free network improves the energy and spectral efficiency of the system, and effectively reduces the performance gaps between UE by ensuring that there are spatially short-range APs that provide stable services to UE.

However, the deployment of cell-free systems in existing commercial mobile networks still faces serious challenges. First, the construction of cell-free systems requires the deployment of the distributed APs throughout the network and the construction of the corresponding fronthaul links, which brings heavy time costs and deployment expenses. Second, simply introducing the cell-free system without cooperation will inevitably cause mutual interference with existing cellular systems, significantly limiting the system performance. Therefore, the deployment of cell-free systems is bound to be a long-term evolutionary process, and hybrid cellular and cell-free cooperation networks are both a necessity and a desirable choice for B5G and 6G.

Some recent works have investigated the performance analysis and resource allocation of hybrid cellular and cell-free networks. A cell-free and legacy cellular coexistence system deployed on the existing system architecture, as well as the corresponding precoding, power control, etc., are outlined in [5]. With appropriate UE association criteria and coordinated beamforming, hybrid cell-free and small cell systems can provide superior downlink rates for static and dynamic UE than the single architecture [6]. However, the above works do not take into account the impact of the spatial distribution of base stations (BSs), APs, and UE on network performance.

Due to the densification and irregularity of wireless node distributions in the network, traditional grid-based deployment models are difficult to reflect the practical system performance. Stochastic geometry models the spatial distribution of wireless nodes with point processes and can effectively characterize the lower bound of the actual system performance. There have been some works using stochastic geometry to analyze the performance of cell-free networks and coordinated multiple points (CoMP) communication in terms of energy efficiency (EE) [7], power control [8] and channel hardening analysis [9], etc. However, there is still a lack of work related to the characterization of hybrid cellular and cell-free networks. In addition, the existing stochastic geometry-based heterogeneous network studies, which separate different network layers from each other [10], are not applicable to the analysis of hybrid cellular and cell-free networks.

To gain some insights of the performance limit of the hybrid network, this paper develops a stochastic geometry-based model for hybrid cellular and cell-free networks, which reveals the coupling of the signal and interference from both the cellular and cell-free networks. However, the aggregate signals from the BSs and APs with conjugate beamforming make it difficult to characterize the distribution of the signal strength and the corresponding signal-to-interference plus noise ratio (SINR). To tackle this issue, we first derive the closed-form expressions for the average signal strength and interference power from the APs, and then the aggregate signal strength distribution is approximated via moment matching. Finally, the coverage probability is characterized on the basis of the Laplace transform of the system interference power. The analysis of network coverage probability is verified by extensive simulations, and it can be used to guide the network deployment and interference management in the hybrid cellular and cell-free networks.

II System Model

As shown in Fig. 1, a hybrid cellular and cell-free network is considered in this paper. The locations of BSs, cell-free APs, and single-antenna UE are modeled by independent homogeneous Poisson point processes (HPPP) ΛB\Lambda_{B}, ΛA\Lambda_{A} and ΛU\Lambda_{U}, with density λB\lambda_{B}/km2\mathrm{km}^{2}, λA\lambda_{A}/km2\mathrm{km}^{2} and λU\lambda_{U}/km2\mathrm{km}^{2}, respectively. Each BS is equipped with NBN_{B} antennas, while each AP is equipped with NAN_{A} antennas. Considering the different configurations that AP and BS can support, PAP_{A} and PBP_{B} denote the maximum downlink power of AP and BS with PA<PBP_{A}<P_{B}. In the network, dmid_{mi} and ljil_{ji} denote the distance between BS mm and UE ii, and that between AP jj and UE ii, respectively. We consider a typical UE, referred as UE 0, which is jointly served by the closest BS, named BS 0, with the distance d00d_{00}, and all the cell-free APs in 𝒜\mathcal{A}. The channel vector between BS mm and UE ii is denoted by 𝐡mi[hmi,1,,hmi,NB]NB×1\mathbf{h}_{mi}\triangleq[h_{mi,1},...,h_{mi,N_{B}}]\in\mathbb{C}^{N_{B}\times 1}, while the channel vector between AP jj and UE ii is 𝐠ji[gji,1,,gji,NA]NA×1\mathbf{g}_{ji}\triangleq[g_{ji,1},...,g_{ji,N_{A}}]\in\mathbb{C}^{N_{A}\times 1}. The channel model consisting of distance-dependent large-scale fading and random small-scale fading is considered as

𝐡mi=βmi12𝜻mi,mωB,\mathbf{h}_{mi}=\beta_{mi}^{\frac{1}{2}}\bm{\zeta}_{mi},m\in\omega_{B}, (1)
𝐠ji=δji12𝝃ji,jωA,\mathbf{g}_{ji}=\delta_{ji}^{\frac{1}{2}}\bm{\xi}_{ji},j\in\omega_{A}, (2)

where βmi\beta_{mi} and δji\delta_{ji} are path loss of the channel with βmi=β0dmiα1\beta_{mi}=\beta_{0}d_{mi}^{-\alpha_{1}} and δji=δ0ljiα2\delta_{ji}=\delta_{0}l_{ji}^{-\alpha_{2}}. ωB\omega_{B} and ωA\omega_{A} are the sets of all the BSs and APs, respectively. The small-scale fading in both 𝜻mi\bm{\zeta}_{mi} and 𝝃ji\bm{\xi}_{ji} are independent and identically distributed (i.i.d.) 𝒞𝒩(0,1)\mathcal{CN}(0,1) random variables (r.v.s).

The entire network area is represented by 𝒜\mathcal{A}.

Refer to caption
Figure 1: Hybrid cellular and cell-free network.

During the downlink transmission, UE in the same cell will be served by the same BS. In addition, both BSs and APs select conjugate beamforming in order to obtain low computational complexity and good performance, and also to avoid channel state information (CSI) interactions between APs [1]. Therefore, the signal transmitted by BS mm is

𝐱B,m=PBηBnϕB,m𝐡mn𝐡mnqn,\mathbf{x}_{B,m}=\sqrt{P_{B}\eta_{B}}\sum_{n\in\phi_{B,m}}\frac{\mathbf{h}_{mn}}{\|\mathbf{h}_{mn}\|}q_{n}, (3)

where ϕB,m\phi_{B,m} denotes the set of UE that are served by BS mm, and qn𝒞𝒩(0,1)q_{n}\sim\mathcal{CN}(0,1) denotes the information-bearing symbols for UE nn. ηB\eta_{B} denotes the power constraint parameter with 𝔼[𝐱B,mH𝐱B,m]=PB\mathbb{E}[\mathbf{x}_{B,m}^{H}\mathbf{x}_{B,m}]=P_{B}. For convenience, ηB\eta_{B} is expressed as the average number of users per BS, i.e., ηB=1|ϕ¯B|=λBλU\eta_{B}=\frac{1}{|\bar{\phi}_{B}|}=\frac{\lambda_{B}}{\lambda_{U}}, where |ϕ¯B||\bar{\phi}_{B}| denotes the average of |ϕB,m||\phi_{B,m}| for any mm.

Denote the set of UE in the network as ϕU\phi_{U}. Therefore, the corresponding downlink signal from each cell-free AP jj is

𝐱A,j=PAηAiϕU𝐠ji𝐠jiqi,\mathbf{x}_{A,j}=\sqrt{P_{A}\eta_{A}}\sum_{i\in\phi_{U}}\frac{\mathbf{g}_{ji}}{\|\mathbf{g}_{ji}\|}q_{i}, (4)

where ηA\eta_{A} denotes the power constraint parameter. Note that the averaged number of UE in ϕU\phi_{U} is 𝔼[|ϕU|]=U¯=λU|𝒜|\mathbb{E}[|\phi_{U}|]=\bar{U}=\lambda_{U}|\mathcal{A}|, ηA\eta_{A} can be denoted as ηA=1U¯\eta_{A}=\frac{1}{\bar{U}} to ensure 𝔼[𝐱A,jH𝐱A,j]=PA\mathbb{E}[\mathbf{x}_{A,j}^{H}\mathbf{x}_{A,j}]=P_{A}.

For any UE ii in the network, ii^{*} is denoted as the index of the associated and nearest BS providing the service. With the collaboration of cell-free APs and cellular BSs, the downlink signal received by the typical UE 0 is

y0=mωB𝐡m0H𝐱B,m+jωA𝐠j0H𝐱A,j+n0=PBηB𝐡00S0Bq0+jωAPAηA𝐠j0S0Aq0+iϕU\0(PBηB𝐡i0H𝐡ii𝐡ii+PAηAjωA𝐠j0H𝐠ji𝐠ji)IUqi+n0,\begin{aligned} y_{0}&=\sum_{m\in\omega_{B}}\mathbf{h}_{m0}^{H}\mathbf{x}_{B,m}+\sum_{j\in\omega_{A}}\mathbf{g}_{j0}^{H}\mathbf{x}_{A,j}+n_{0}\\ &=\underbrace{\sqrt{P_{B}\eta_{B}}\|\mathbf{h}_{00}\|}_{S_{0B}}q_{0}+\underbrace{\sum_{j\in\omega_{A}}\sqrt{P_{A}\eta_{A}}\|\mathbf{g}_{j0}\|}_{S_{0A}}q_{0}+\\ &\underbrace{\sum_{i\in\phi_{U}\backslash_{0}}\!\Big{(}\sqrt{P_{B}\eta_{B}}\mathbf{h}_{i^{*}0}^{H}\frac{\mathbf{h}_{i^{*}i}}{\|\mathbf{h}_{i^{*}i}\|}\!+\!\sqrt{P_{A}\eta_{A}}\sum_{j\in\omega_{A}}\mathbf{g}_{j0}^{H}\frac{\mathbf{g}_{ji}}{\|\mathbf{g}_{ji}\|}\Big{)}}_{I_{U}}q_{i}+n_{0},\end{aligned}

(5)

where the first term S0AS_{0A} and the second term S0BS_{0B} represent the desired signals from BS 0 and cell-free APs, respectively. The total interference is shown in the third term IUI_{U}. Each term in IUI_{U} consists of the signal sent by cellular BSs and cell-free APs to any other UE. The last term n0n_{0} denotes the additive white Gaussian noise (AWGN) with power σ2\sigma^{2}.

Based on (5), the interference power caused by the signal intended to UE ii is given by

Ii=|PBηB𝐡i0H𝐡ii𝐡ii+PAηAjωA𝐠j0H𝐠ji𝐠ji|2.I_{i}=\Big{|}\sqrt{P_{B}\eta_{B}}\mathbf{h}_{i^{*}0}^{H}\frac{\mathbf{h}_{i^{*}i}}{\|\mathbf{h}_{i^{*}i}\|}\!+\!\sqrt{P_{A}\eta_{A}}\sum_{j\in\omega_{A}}\mathbf{g}_{j0}^{H}\frac{\mathbf{g}_{ji}}{\|\mathbf{g}_{ji}\|}\Big{|}^{2}. (6)

In interference IiI_{i}, BS channel vector 𝐡i0\mathbf{h}_{i^{*}0} is independent of channel vector 𝐠j0,jωA\mathbf{g}_{j0},\forall j\in\omega_{A}. Meanwhile, the channel gains 𝐠i0\mathbf{g}_{i0} and 𝐠j0\mathbf{g}_{j0} from different APs are also independent of each other, ij\forall i\neq j. Taking into account the law of large number and the mutual independence of channels as well as beamforming vectors between different BSs and APs, IiI_{i} can be approximated as

IiPBηB|𝐡i0H𝐡ii𝐡ii|2+PAηAjωA|𝐠j0H𝐠ji𝐠ji|2.I_{i}\approx P_{B}\eta_{B}\Big{|}\mathbf{h}_{i^{*}0}^{H}\frac{\mathbf{h}_{i^{*}i}}{\|\mathbf{h}_{i^{*}i}\|}\Big{|}^{2}+P_{A}\eta_{A}\sum_{j\in\omega_{A}}\Big{|}\mathbf{g}_{j0}^{H}\frac{\mathbf{g}_{ji}}{\|\mathbf{g}_{ji}\|}\Big{|}^{2}. (7)

The approximation in (7) indicates that IiI_{i} can be expressed in the form of the sum of the power of the signal from the associated BS ii^{*} and each AP. Further, by classifying the interference into intra-cell interference IB0I_{B0}, inter-cell interference IBI_{B}, and interference IAI_{A} due to the APs, the total interference iϕU\{0}Ii\sum_{i\in\phi_{U}\backslash\{0\}}I_{i} can be rewritten as

iϕU\{0}Ii=IB0+IB+IA,\sum_{i\in\phi_{U}\backslash\{0\}}I_{i}=I_{B0}+I_{B}+I_{A}, (8)

where

IB0\displaystyle I_{B0} =PBηBnϕB,0\{0}|𝐡00H𝐡0n𝐡0n|2,\displaystyle=P_{B}\eta_{B}\sum_{n\in\phi_{B,0}\backslash\{0\}}\Big{|}\mathbf{h}_{00}^{H}\frac{\mathbf{h}_{0n}}{\|\mathbf{h}_{0n}\|}\Big{|}^{2}, (9)
IB\displaystyle I_{B} =PBηBmωB\{0}nϕB,m|𝐡m0H𝐡mn𝐡mn|2,\displaystyle=P_{B}\eta_{B}\sum_{m\in\omega_{B}\backslash\{0\}}\sum_{n\in\phi_{B,m}}\Big{|}\mathbf{h}_{m0}^{H}\frac{\mathbf{h}_{mn}}{\|\mathbf{h}_{mn}\|}\Big{|}^{2},
IA\displaystyle I_{A} =PAηAiϕU\{0}jωA|𝐠j0H𝐠ji𝐠ji|2.\displaystyle=P_{A}\eta_{A}\sum_{i\in\phi_{U}\backslash\{0\}}\sum_{j\in\omega_{A}}\Big{|}\mathbf{g}_{j0}^{H}\frac{\mathbf{g}_{ji}}{\|\mathbf{g}_{ji}\|}\Big{|}^{2}.

Therefore, the corresponding received SINR at UE 0 is approximately expressed as

Ω=S0IB0+IB+IA+σ2,\Omega=\frac{S_{0}}{I_{B0}+I_{B}+I_{A}+\sigma^{2}}, (10)

where

S0=(S0B+S0A)2=(PBηB𝐡00+PAηAjωA𝐠j0)2.\begin{aligned} S_{0}&=\big{(}S_{0B}+S_{0A}\big{)}^{2}=\Big{(}\sqrt{P_{B}\eta_{B}}\|\mathbf{h}_{00}\|+\sqrt{P_{A}\eta_{A}}\sum_{j\in\omega_{A}}\|\mathbf{g}_{j0}\|\Big{)}^{2}.\end{aligned}

(11)

III Analysis of Signal Strength and Interference

In this section, the statistical distributions of the received signal and interference power are characterized. The signal strength is approximated via moment matching, with its first- and second-order moments derived in closed-form. The intra- and inter-cell interference caused by BSs are approximated as a Gamma r.v. and a weighted sum of Gamma r.v.s, respectively. The average interference caused by cell-free APs is derived in closed-form. In addition, the performance of the network can be obtained by analyzing a typical UE 0 according to Slivnyak’s theorem [11].

III-A Analysis of Channel Distribution

Based on the channel model of BSs and APs, the power of the channel to UE ii for the mmth BS and the jjth AP can be respectively given by

|𝐡mi|2=βmi𝜻miH𝜻mi,|\mathbf{h}_{mi}|^{2}=\beta_{mi}\bm{\zeta}_{mi}^{H}\bm{\zeta}_{mi}, (12)
|𝐠ji|2=δji𝝃jiH𝝃ji.|\mathbf{g}_{ji}|^{2}=\delta_{ji}\bm{\xi}_{ji}^{H}\bm{\xi}_{ji}. (13)

Since all the entries in both 𝜻mi\bm{\zeta}_{mi} and 𝝃ji\bm{\xi}_{ji} follow the i.i.d. 𝒞𝒩(0,1)\mathcal{CN}(0,1), 𝜻mi\bm{\zeta}_{mi} and 𝝃ji\bm{\xi}_{ji} are isotropic vectors in NBN_{B} and NAN_{A} dimensions respectively [12].

Note that for the isotropic vector 𝐱N×1\mathbf{x}\in\mathbb{C}^{N\times 1} with each entry following i.i.d. 𝒞𝒩(1,δ2)\mathcal{CN}(1,\delta^{2}), 𝐱H𝐱\mathbf{x}^{H}\mathbf{x} is the sum of i.i.d. variables Γ(1,δ2)\Gamma(1,\delta^{2}), and thus follows Γ(N,δ2)\Gamma(N,\delta^{2}) [13]. Therefore, we have 𝜻00H𝜻00Γ(NB,1)\bm{\zeta}_{00}^{H}\bm{\zeta}_{00}\sim\Gamma(N_{B},1) and 𝝃j0H𝝃j0Γ(NA,1)\bm{\xi}_{j0}^{H}\bm{\xi}_{j0}\sim\Gamma(N_{A},1).

Lemma 1.

For the Gamma distributed r.v. XΓ(a,θ)X\sim\Gamma(a,\theta) and any b>0b>0, Y=bXΓ(a,bθ)Y=bX\sim\Gamma(a,b\theta) [14].

Based on Lemma 1, the BS and AP channel power in (12) and (13) are distributed according to

|𝐡mi|2Γ(NB,βmi),|\mathbf{h}_{mi}|^{2}\sim\Gamma(N_{B},\beta_{mi}), (14)
|𝐠ji|2Γ(NA,δji),|\mathbf{g}_{ji}|^{2}\sim\Gamma(N_{A},\delta_{ji}), (15)

III-B Approximation of the Signal Power Distribution

According to (14), the power of the nearest associated BS channel |𝐡00|2|\mathbf{h}_{00}|^{2} is the sum of NBN_{B} i.i.d. variables following Γ(1,β00)\Gamma(1,\beta_{00}), i.e., |𝐡00|2Γ(NB,β00)|\mathbf{h}_{00}|^{2}\sim\Gamma(N_{B},\beta_{00}). For further analysis of the desired signal S0S_{0} in (9), Lemma 2 about the square root of Gamma variable is first introduced.

Lemma 2.

For any Gamma distributed r.v. XΓ(k,θ)X\sim\Gamma(k,\theta), the square root YY of XX follows the Nakagami distribution as Y=XNakagami(m,ω)Y=\sqrt{X}\sim\mathrm{Nakagami}(m,\omega) [15], where the parameters are m=k,ω=mθm=k,\omega=m\theta.

Therefore, the distribution of 𝐡00\|\mathbf{h}_{00}\| is obtained according to Lemma 2 as

𝐡00=|𝐡00|2Nakagami(NB,NBβ00),\|\mathbf{h}_{00}\|=\sqrt{|\mathbf{h}_{00}|^{2}}\sim\mathrm{Nakagami}(N_{B},N_{B}\beta_{00}), (16)

while the component of AP channel 𝐠j0\|\mathbf{g}_{j0}\| in S0S_{0} has

𝐠j0=|𝐠j0|2Nakagami(NA,NAδj0),jωA.\|\mathbf{g}_{j0}\|=\sqrt{|\mathbf{g}_{j0}|^{2}}\sim\mathrm{Nakagami}(N_{A},N_{A}\delta_{j0}),\forall j\in\omega_{A}. (17)

The distribution of the desired signal S0S_{0} is composed of the signals from the associated BS 0 together with all APs. Considering the random distribution of the cell-free APs in the network, the following Lemma 3 is introduced.

Lemma 3.

With the law of large number, the desired signal in S0S_{0} due to the APs can be approximated by their average LAL_{A} when the number of APs is large and α2<4\alpha_{2}<4, i.e.,

PAηA\displaystyle\sqrt{P_{A}\eta_{A}} jωA𝐠j0PAηA𝔼[jωA𝐠j0]\displaystyle\sum_{j\in\omega_{A}}\|\mathbf{g}_{j0}\|\approx\sqrt{P_{A}\eta_{A}}\mathbb{E}[\sum_{j\in\omega_{A}}\|\mathbf{g}_{j0}\|] (18)
=4πρAλAδ0124α2Γ(NA+12)Γ(NA)(|𝒜|π)1α24LA,\displaystyle=\underbrace{\frac{4\pi\sqrt{\rho_{A}}\lambda_{A}\delta_{0}^{\frac{1}{2}}}{4-\alpha_{2}}\frac{\Gamma(N_{A}+\frac{1}{2})}{\Gamma(N_{A})}\Big{(}\frac{|\mathcal{A}|}{\pi}\Big{)}^{1-\frac{\alpha_{2}}{4}}}_{L_{A}},

where ρA=PAηA\rho_{A}=P_{A}\eta_{A}. The detailed derivation is based on the Campbell Theorem [11], and will be shown in an extended journal version.

From Lemma 3, the power expression S0S_{0} for the desired signal is simplified as the square of the sum of a Nakagami r.v. and the constant LAL_{A} as S0(PBηB𝐡00+LA)2S_{0}\approx(\sqrt{P_{B}\eta_{B}}\|\mathbf{h}_{00}\|+L_{A})^{2}. Therefore, the following Lemma is introduced.

Lemma 4.

For any Nakagami r.v. XNakagami(m,ω)X\sim\mathrm{Nakagami}(m,\omega), the probability density function (PDF) of the square of the shifted Nakagami r.v. Y=(X+A)2Y=(X+A)^{2} for Y>A2Y>A^{2} is

fY(y)=mmΓ(m)ωm(yA)2m1exp(mω(yA)2)y12.\begin{aligned} f_{Y}(y)&=\!\frac{m^{m}}{\Gamma(m)\omega^{m}}\!(\!\sqrt{y}\!-\!A)^{2m\!-\!1}\mathrm{exp}\!\big{(}\!-\!\frac{m}{\omega}(\sqrt{y}\!-\!A)^{2}\big{)}y^{\frac{1}{2}}.\end{aligned}

(19)
Refer to caption
Figure 2: The distribution of the square of shifted Nakagami r.v. Y=(X+A)2Y=(X+A)^{2}.

The verification of the distribution of Y=(X+A)2Y=(X+A)^{2} is shown in Fig. 2. From (19) and Fig. 2, the exact distribution of S0S_{0} is difficult to characterize, but the corresponding PDF of S0S_{0} has a similar structure to that of the Gamma distribution. Therefore, with given distance of the nearest associated BS 0, S0S_{0} can be approximated as a Gamma r.v. based on its first- and second-order moments [16]. The corresponding Lemma (5) is introduced as follows.

Lemma 5.

According to the definition of the Gamma r.v. [17], the desired signal power S0S_{0} can be approximated as the Gamma distribution Γ(kS0,θS0)\Gamma(k_{S_{0}},\theta_{S_{0}}) with

kS0\displaystyle k_{S_{0}} =(𝔼[S0])2Var{S0}=(𝔼[S0])2𝔼[S02](𝔼[S0])2,\displaystyle=\frac{\big{(}\mathbb{E}[S_{0}]\big{)}^{2}}{\mathrm{Var}\{S_{0}\}}=\frac{\big{(}\mathbb{E}[S_{0}]\big{)}^{2}}{\mathbb{E}[S_{0}^{2}]-\big{(}\mathbb{E}[S_{0}]\big{)}^{2}}, (20)
θS0\displaystyle\theta_{S_{0}} =Var{S0}𝔼[S0]=𝔼[S02](𝔼[S0])2𝔼[S0],\displaystyle=\frac{\mathrm{Var}\{S_{0}\}}{\mathbb{E}[S_{0}]}=\frac{\mathbb{E}[S_{0}^{2}]-\big{(}\mathbb{E}[S_{0}]\big{)}^{2}}{\mathbb{E}[S_{0}]},

where the first- and second-order moments of S0S_{0} are

𝔼[S0]=ρBNBβ00+2ρB12LAΓ(NB+12)Γ(NB)β0012+LA2,\mathbb{E}[S_{0}]=\rho_{B}N_{B}\beta_{00}+2\rho_{B}^{\frac{1}{2}}L_{A}\frac{\Gamma(N_{B}+\frac{1}{2})}{\Gamma(N_{B})}\beta_{00}^{\frac{1}{2}}+L_{A}^{2}, (21)
𝔼[S02]\displaystyle\mathbb{E}[S_{0}^{2}] =ρB2NB(NB+1)β002+4ρB32LAΓ(NB+32)Γ(NB)β0032\displaystyle=\rho_{B}^{2}N_{B}(N_{B}+1)\beta_{00}^{2}+4\rho_{B}^{\frac{3}{2}}L_{A}\frac{\Gamma(N_{B}+\frac{3}{2})}{\Gamma(N_{B})}\beta_{00}^{\frac{3}{2}} (22)
+6ρBLA2NBβ00+4ρB12LA3Γ(NB+12)Γ(NB)β0012+LA4.\displaystyle+6\rho_{B}L_{A}^{2}N_{B}\beta_{00}+4\rho_{B}^{\frac{1}{2}}L_{A}^{3}\frac{\Gamma(N_{B}+\frac{1}{2})}{\Gamma(N_{B})}\beta_{00}^{\frac{1}{2}}+L_{A}^{4}.

The detailed derivation is based on the raw moments of Gamma distribution, and is omitted here for space.

III-C Analysis of Interference Power Distribution

Similar to the case of the desired signal, the power distribution of the interference is analyzed in this subsection. Considering that conjugate beamforming is applied by both BSs and APs in the network, the Lemma 6 for the projection of isotropic channel vectors is introduced.

Lemma 6.

Denote 𝐱N×1\mathbf{x}\in\mathbb{C}^{N\times 1} as an isotropic vector with i.i.d. 𝒞𝒩(0,θ)\mathcal{CN}(0,\theta) entries. If 𝐱\mathbf{x} is projected onto an s-dimensional beamforming subspace, the power distribution is [18]

|𝐱H𝐰|2Γ(s,θ).|\mathbf{x}^{H}\mathbf{w}|^{2}\sim\Gamma(s,\theta). (23)

Based on Lemma 6, the power IB0I_{B0} of intra-cell interference in (9) can be approximated as the sum of (|ϕ¯B|1)(|\bar{\phi}_{B}|-1) i.i.d. variables following Γ(1,PBηBβ00)\Gamma(1,P_{B}\eta_{B}\beta_{00}). Further, extracting the scale parameter, the power of intra-cell interference can be rewritten as IB0=PBηBβ00κB,0I_{B0}=P_{B}\eta_{B}\beta_{00}\kappa_{B,0}, where κB,0Γ(|ϕ¯B|1,1)\kappa_{B,0}\sim\Gamma(|\bar{\phi}_{B}|-1,1).

For the inter-cell interference, since 𝐡m0\mathbf{h}_{m0} is also independent of 𝐡mn\mathbf{h}_{mn}, the interference power of each BS mωB\{0}m\in\omega_{B}\backslash\{0\} in IBI_{B} is approximated as nϕB,m|𝐡m0H𝐡mn𝐡mn|2Γ(|ϕ¯B|,βm0)\sum_{n\in\phi_{B,m}}\Big{|}\mathbf{h}_{m0}^{H}\frac{\mathbf{h}_{mn}}{\|\mathbf{h}_{mn}\|}\Big{|}^{2}\sim\Gamma(|\bar{\phi}_{B}|,\beta_{m0}). Therefore, as the sum of interference from BSs in ωB\{0}\omega_{B}\backslash\{0\}, the inter-cell interference IBI_{B} can be further expressed as the sum of Gamma variables with the same shape parameters and scale parameters, i.e.,

IB=PBηBmωB\{0}βm0κB,m0,I_{B}=P_{B}\eta_{B}\sum_{m\in\omega_{B}\backslash\{0\}}\beta_{m0}\kappa_{B,m0}, (24)

where κB,m0Γ(|ϕ¯B|,1),mωB\{0}\kappa_{B,m0}\in\Gamma(|\bar{\phi}_{B}|,1),\forall m\in\omega_{B}\backslash\{0\}.

Next, we need to analyze the interference IAI_{A} from the APs. According to (3) and (6), the following Lemma about IAI_{A} is introduced.

Lemma 7.

By the law of large number, the interference IAI_{A} due to the APs is approximated by its average I¯A\bar{I}_{A} when the number of APs is large and α2<2\alpha_{2}<2, i.e.,

IA\displaystyle I_{A} PAηA𝔼[iϕU\{0}jωA|𝐠j0H𝐠ji𝐠ji|2]\displaystyle\approx P_{A}\eta_{A}\mathbb{E}\bigg{[}\sum_{i\in\phi_{U}\backslash\{0\}}\sum_{j\in\omega_{A}}\Big{|}\mathbf{g}_{j0}^{H}\frac{\mathbf{g}_{ji}}{\|\mathbf{g}_{ji}\|}\Big{|}^{2}\bigg{]} (25)
=2πρAλAδ0(λU|𝒜|1)2α2(|𝒜|π)1α22I¯A.\displaystyle=\underbrace{\frac{2\pi\rho_{A}\lambda_{A}\delta_{0}(\lambda_{U}|\mathcal{A}|-1)}{2-\alpha_{2}}\Big{(}\frac{|\mathcal{A}|}{\pi}\Big{)}^{1-\frac{\alpha_{2}}{2}}}_{\bar{I}_{A}}.

The detailed derivation is based on the Campbell Theorem [11], and will be shown in an extended journal version.

IV Coverage Probability of Hybrid Cellular and Cell-free Network

In this section, the coverage probability of hybrid cellular and cell-free network is analyzed based on the distribution of signal strength and various interference components, derived in the preceding section. In general, the coverage probability is the complementary cumulative distribution function (CCDF) of SINR over the overall network, which can be defined as

pc[Ω=S0IB0+IB+I¯A+σ2>T],p_{\mathrm{c}}\triangleq\mathbb{P}[\Omega=\frac{S_{0}}{I_{B0}+I_{B}+\bar{I}_{A}+\sigma^{2}}>T], (26)

where TT denotes the target threshold of the SINR Ω\Omega.

IV-A Analysis of Coverage Probability

Taking the distance d00d_{00} between the typical UE 0 and its associated and nearest BS 0 as an r.v., the average coverage probability in the network is

pc\displaystyle p_{\mathrm{c}} =𝔼[pc(d00)]=0|𝒜|πpc(r)fd00(r)dr,\displaystyle=\mathbb{E}\big{[}p_{\mathrm{c}}(d_{00})\big{]}=\int_{0}^{\sqrt{\frac{|\mathcal{A}|}{\pi}}}p_{\mathrm{c}}(r)f_{d_{00}}(r)\mathrm{d}r, (27)

where fd00(r)f_{d_{00}}(r) denotes the PDF of the nearest point distance in PPP. With the cumulative distribution function (CDF) of r.v. d00d_{00} as Fd00(r)=1eλBπr2F_{d_{00}}(r)=1-e^{-\lambda_{B}\pi r^{2}} [11], there is

fd00(r)\displaystyle f_{d_{00}}(r) =dFd00(r)dr\displaystyle=\frac{\mathrm{d}F_{d_{00}}(r)}{\mathrm{d}r} =2λBπreλBπr2.\displaystyle=2\lambda_{B}\pi re^{-\lambda_{B}\pi r^{2}}. (28)

First, the relationship between intra-cell interference IB0I_{B0} and inter-cell interference IBI_{B} is analyzed. Clearly, both IB0I_{B0} and IBI_{B} are dependent on the distance d00d_{00}, i.e., IB0I_{B0} comes from the associated BS 0 with a distance of d00d_{00}, and IBI_{B} comes from the other BSs with distances dd00d\geq d_{00}. However, there is no interaction between IB0I_{B0} and IBI_{B}. Specifically, with the given d00d_{00}, IB0I_{B0} depends on the distribution of UE in the cell of BS 0, while IBI_{B} depends mainly on the distribution of other BSs with a distance no smaller than d00d_{00}. Therefore, IB0I_{B0} and IBI_{B} are independent of each other with a given d00d_{00}. Therefore, the coverage probability can be further expressed as in Lemma 8.

Lemma 8.

Considering that the desired signal S0S_{0} following the Gamma distribution, i.e., S0Γ(kS0,θS0)S_{0}\sim\Gamma(k_{S_{0}},\theta_{S_{0}}) the network coverage probability in (26) can be expressed as

pc(d00)=[S0>T(IB0+IB+I¯A+σ2)]\displaystyle p_{\mathrm{c}}(d_{00})=\mathbb{P}[S_{0}>T(I_{B0}+I_{B}+\bar{I}_{A}+\sigma^{2})] (29)
=i=0kS01(1)ii!iis{esTIeθS0YIB0(s)YIB(s)}s=1,\displaystyle=\sum_{i=0}^{k_{S_{0}}-1}\frac{(-1)^{i}}{i!}\frac{\partial^{i}}{\partial^{i}s}\Big{\{}e^{-s\frac{TI_{e}}{\theta_{S_{0}}}}\mathcal{L}_{Y_{I_{B0}}}(s)\mathcal{L}_{Y_{I_{B}}}(s)\Big{\}}_{s=1},

where the sum of interference from APs and noise is denoted as Ie=I¯A+σ2I_{e}=\bar{I}_{A}+\sigma^{2}. The shape parameter kS0k_{S_{0}} is integer. The Laplace transforms of YIB0=TIB0θS0Y_{I_{B0}}=\frac{TI_{B0}}{\theta_{S_{0}}} and YIB=TIBθS0Y_{I_{B}}=\frac{TI_{B}}{\theta_{S_{0}}} are

YIB0(s)=(1+sTρBβ0d00α1θS0)1|ϕ¯B|,YIB(s)=exp(2πλBd00|𝒜|π[(1+sTρBβ0rα1θS0)|ϕ¯B|1]rdr).\begin{aligned} &\mathcal{L}_{Y_{I_{B0}}}(s)=\Big{(}1+s\frac{T\rho_{B}\beta_{0}d_{00}^{-\alpha_{1}}}{\theta_{S_{0}}}\Big{)}^{1-|\bar{\phi}_{B}|},\\ &\mathcal{L}_{Y_{I_{B}}}(s)=\mathrm{exp}\Big{(}2\pi\lambda_{B}\int_{d_{00}}^{\sqrt{\frac{|\mathcal{A}|}{\pi}}}\big{[}\big{(}1+s\frac{T\rho_{B}\beta_{0}r^{-\alpha_{1}}}{\theta_{S_{0}}}\big{)}^{-|\bar{\phi}_{B}|}-1\big{]}r\mathrm{d}r\Big{)}.\end{aligned}

(30)

Based on Lemma 8, the analysis of the coverage probability is transformed into the analysis of the higher-order derivatives, and the coverage of probability is rewritten as

pc(d00)\displaystyle p_{\mathrm{c}}(d_{00}) =i=0kS01(1)ii!iis{L(s)}s=1,\displaystyle=\sum_{i=0}^{k_{S_{0}}-1}\frac{(-1)^{i}}{i!}\frac{\partial^{i}}{\partial^{i}s}\Big{\{}L(s)\Big{\}}_{s=1}, (31)

where

L(s)=esTIeθS0(1+sTρBβ0d00α1θS0)1|ϕ¯B|\displaystyle L(s)=e^{-s\frac{TI_{e}}{\theta_{S_{0}}}}\cdot\Big{(}1+s\frac{T\rho_{B}\beta_{0}d_{00}^{-\alpha_{1}}}{\theta_{S_{0}}}\Big{)}^{1-|\bar{\phi}_{B}|} (32)
exp(2πλBd00|𝒜|π[(1+sTρBβ0rα1θS0)|ϕ¯B|1]rdr).\displaystyle\cdot\mathrm{exp}\Big{(}2\pi\lambda_{B}\int_{d_{00}}^{\sqrt{\frac{|\mathcal{A}|}{\pi}}}\big{[}\big{(}1+s\frac{T\rho_{B}\beta_{0}r^{-\alpha_{1}}}{\theta_{S_{0}}}\big{)}^{-|\bar{\phi}_{B}|}-1\big{]}r\mathrm{d}r\Big{)}.

The higher-order derivatives of L(s)L(s) is derived in the next part.

IV-B Evaluation of Higher-order Derivatives

The objective function L(s)L(s) of the higher-order derivatives in (31) is rewritten in the form of the exponential function, i.e.,

L(s)\displaystyle L(s) =exp{sTIeθS0D1(s)+(1|ϕ¯B|)ln(1+sTθS0d00α1)D2(s)\displaystyle=\mathrm{exp}\bigg{\{}\underbrace{-s\frac{TI_{e}}{\theta_{S_{0}}}}_{D_{1}(s)}+\underbrace{(1-|\bar{\phi}_{B}|)\mathrm{ln}\Big{(}1+sT_{\theta_{S_{0}}}d_{00}^{-\alpha_{1}}\Big{)}}_{D_{2}(s)} (33)
+2πλBd00|𝒜|π[(1+sTθS0rα1)|ϕ¯B|1]rdrD3(s)},\displaystyle+\underbrace{2\pi\lambda_{B}\int_{d_{00}}^{\sqrt{\frac{|\mathcal{A}|}{\pi}}}\big{[}\big{(}1+sT_{\theta_{S_{0}}}r^{-\alpha_{1}}\big{)}^{-|\bar{\phi}_{B}|}-1\big{]}r\mathrm{d}r}_{D_{3}(s)}\bigg{\}},

where TθS0=TρBβ0θS0T_{\theta_{S_{0}}}=\frac{T\rho_{B}\beta_{0}}{\theta_{S_{0}}} is applied for convenience.

Since L(s)L(s) is a composite function of g(s)=D1(s)+D2(s)+D3(s)g(s)=D_{1}(s)+D_{2}(s)+D_{3}(s), the special case of Faà di Bruno’s formula with exponential functions can be applied to efficiently derive the iith order derivatives of L(s)L(s) [16, 19], i.e.,

iisL(s)=iis{exp(g(s))}=exp(g(s))Bi(1g(s)1s,,ig(s)is),\begin{aligned} \frac{\partial^{i}}{\partial^{i}s}L(s)&=\frac{\partial^{i}}{\partial^{i}s}\big{\{}\mathrm{exp}\big{(}g(s)\big{)}\big{\}}=\mathrm{exp}\big{(}g(s)\big{)}B_{i}\Big{(}\frac{\partial^{1}g(s)}{\partial^{1}s},...,\frac{\partial^{i}g(s)}{\partial^{i}s}\Big{)},\end{aligned}

(34)

where Bi(x1,,xi)B_{i}(x_{1},...,x_{i}) denotes the iith complete exponential Bell polynomial, whose coefficients can be efficiently obtained according to its definition [20, 21]. The remaining work is to evaluate the higher-order derivatives of g(s)g(s), which can be decomposed as

ig(s)is=iD1(s)is+iD2(s)is+iD3(s)is.\frac{\partial^{i}g(s)}{\partial^{i}s}=\frac{\partial^{i}D_{1}(s)}{\partial^{i}s}+\frac{\partial^{i}D_{2}(s)}{\partial^{i}s}+\frac{\partial^{i}D_{3}(s)}{\partial^{i}s}. (35)

For D1(s)D_{1}(s), the derivatives from order 1 to order (kS01)(k_{S_{0}}-1) can be expressed respectively as

iD1(s)is={TIeθS0,i=10,i>1\frac{\partial^{i}D_{1}(s)}{\partial^{i}s}=\left\{\begin{aligned} -\frac{TI_{e}}{\theta_{S_{0}}},\quad i=1\\ 0,\quad i>1\end{aligned}\right. (36)

Additionally, for D2(s)D_{2}(s), there is

iD2(s)is=(1)i1(1|ϕ¯B|)(i1)!(TθS0d00α11+TθS0d00α1s)i.\frac{\partial^{i}D_{2}(s)}{\partial^{i}s}=(-1)^{i-1}(1-|\bar{\phi}_{B}|)(i-1)!\Big{(}\frac{T_{\theta_{S_{0}}}d_{00}^{-\alpha_{1}}}{1+T_{\theta_{S_{0}}}d_{00}^{-\alpha_{1}}s}\Big{)}^{i}. (37)

Finally, the higher-order derivatives of D3(s)D_{3}(s) is

iD3(s)is=\displaystyle\frac{\partial^{i}D_{3}(s)}{\partial^{i}s}= (38)
2πλBd00|𝒜|π(|ϕ¯B|+i1)!(|ϕ¯B|1)!(TθS0rα1)i(1+TθS0rα1s)|ϕ¯B|+irdr.\displaystyle 2\pi\lambda_{B}\int_{d_{00}}^{\sqrt{\frac{|\mathcal{A}|}{\pi}}}\frac{(|\bar{\phi}_{B}|+i-1)!}{(|\bar{\phi}_{B}|-1)!}\cdot\frac{(-T_{\theta_{S_{0}}}r^{-\alpha_{1}})^{i}}{(1+T_{\theta_{S_{0}}}r^{-\alpha_{1}}s)^{|\bar{\phi}_{B}|+i}}r\mathrm{d}r.

Finally, the network coverage probability can be obtained by substituting (31) with (36), (37) and (38) back into (27).

V Simulation Results

In this section, the analytical results of the coverage probability of the hybrid cell and cell-free network are verified by the comparison with the Monte-Carlo (MC) simulation results. Each result of the MS simulation is averaged from 1000 randomly generated wireless node distributions with 5 realizations per channel. All the wireless nodes are randomly distributed in a circular area of radius 500m and UE 0 is located at the center of the circle. The densities of BSs, APs and UE are λB=40/km2\lambda_{B}=40/\mathrm{km}^{2}, λA=200/km2\lambda_{A}=200/\mathrm{km}^{2} and λU=160/km2\lambda_{U}=160/\mathrm{km}^{2}, respectively. Other relevant parameters are as follows: α1=2.7\alpha_{1}=2.7, α2=1.8\alpha_{2}=1.8, PBσ2=130\frac{P_{B}}{\sigma^{2}}=130dB, PA=3×105PBP_{A}=3\times 10^{-5}P_{B}, NB=4N_{B}=4, NA=2N_{A}=2, C=3×108C=3\times 10^{8}m/s, f=3.5f=3.5GHz and β0=δ0=(C4πf)2\beta_{0}=\delta_{0}=(\frac{C}{4\pi f})^{2}.

Fig. 3 shows the coverage probability in cellular networks (PA=0P_{A}=0), cell-free networks (PB=0P_{B}=0), and hybrid cellular and cell-free networks for different SINR thresholds TT. The coverage probability is obtained from the linear weighted probability of the upper and lower integers of kθSk_{\theta_{S}}, i.e.,

pc=(kθSkθS)pc,kθS+(kθSkθS)pc,kθS.p_{\mathrm{c}}=(\left\lceil k_{\theta_{S}}\right\rceil-k_{\theta_{S}})p_{\mathrm{c,\left\lfloor k_{\theta_{S}}\right\rfloor}}+(k_{\theta_{S}}-\left\lfloor k_{\theta_{S}}\right\rfloor)p_{\mathrm{c,\left\lceil k_{\theta_{S}}\right\rceil}}. (39)

From Fig. 3, It is expected that the coverage probability analysis of the hybrid network is generally consistent with the results of MC simulation under different SINR threshold, and can also be applied to the special case where PA=0P_{A}=0. Compared with traditional cellular networks, hybrid networks effectively improve the communication performance of edge UE and reduce the performance gaps between UE. Compared with cell-free networks, such hybrid networks can achieve higher peak SINR. Therefore, by deploying low-power APs, hybrid cellular and cell-free networks can provide UE with uniformly good communication services while obtaining better peak SINR performance.

Refer to caption
Figure 3: Coverage probability of different architectures under different TT.

VI Conclusion

In this paper, the hybrid cellular and cell-free network is modeled by the stochastic geometry approach, revealing the coupling of the signal and interference from both the cellular and cell-free networks. Moment matching is used to approximate the aggregate signal received from the hybrid network to address the difficulty of distribution analysis due to conjugate beamforming. The coverage probability is then obtained by the Laplace transform for interference. The analysis of the coverage probability of hybrid networks is validated by MC simulation, demonstrating that hybrid networks can reduce the performance gap while improving the peak SINR performance.

VII Acknowledgment

This work was supported by the National Key R&D Program of China with Grant number 2019YFB1803400, and by the National Natural Science Foundation of China with grant number 62071114.

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